Sensing circuit for programmable resistive device using diode as program selector

ABSTRACT

A sensing circuit for programmable resistive device using diode as program selector is disclosed. The sensing circuit can have a reference and a sensing branch. In one embodiment, each branch can have a first type of MOS with the source coupled to a first supply voltage, the drain coupled to the drain of a second type of MOS, which can have the gate coupled to a bias supply voltage. The sources of the second type of MOS in the reference and sensing branches can be coupled to a reference resistor and a programmable resistance element, respectively, and they are further coupled to a second supply voltage through their diodes. The gate of the first type of MOS in the sensing branch can be coupled to the gate of the first type of MOS in the reference branch, which can have the drain coupled to the gate. The resistance difference between the reference resistor and the programmable resistive element can be sensed through the drain of the first type of MOS in the sensing branch into a logic level.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application claims priority benefit of U.S. Provisional Patent Application No. 61/375,653, filed on Aug. 20, 2010 and entitled “CIRCUIT AND SYSTEM OF USING JUNCTION DIODE AS PROGRAM SELECTOR FOR RESISTIVE DEVICES IN CMOS LOGIC PROCESSES,” which is hereby incorporated herein by reference; and U.S. Provisional Patent Application No. 61/375,660, filed on Aug. 20, 2010 and entitled “CIRCUIT AND SYSTEM OF USING POLYSILICON DIODE AS PROGRAM SELECTOR FOR RESISTIVE DEVICES IN CMOS LOGIC PROCESSES,” which is hereby incorporated herein by reference.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to programmable memory devices, such as programmable resistive devices for use in memory arrays.

2. Description of the Related Art

A programmable resistive device is generally referred to a device's resistance states that may change after means of programming. Resistance states can also be determined by resistance values. For example, a resistive device can be a One-Time Programmable (OTP) device, such as electrical fuse, and the programming means can be applying a high voltage to induce a high current to flow through the OTP element, such as fuse. When a high current flows through an OTP element by turning on a program selector, the OTP element can be programmed, or burned into a high or low resistance state (depending on either fuse or anti-fuse).

An electrical fuse is a common OTP which is a programmable resistive device that can be constructed from a segment of interconnect, such as polysilicon, silicided polysilicon, silicide, metal, metal alloy, or some combination thereof. The metal can be aluminum, copper, or other transition metals. One of the most commonly used electrical fuses is a CMOS gate, fabricated in silicided polysilicon, used as interconnect. The electrical fuse can also be one or more contacts or vias instead of a segment of interconnect. A high current may blow the contact(s) or via(s) into a very high resistance state. The electrical fuse can be an anti-fuse, where a high voltage makes the resistance lower, instead of higher. The anti-fuse can consist of one or more contacts or vias with an insulator in between. The anti-fuse can also be a CMOS gate coupled to a CMOS body with a thin gate oxide as insulator.

The programmable resistive device can be a reversible resistive device that can be programmed into a digital logic value “0” or “1” repetitively and reversibly. The programmable resistive device can be fabricated from phase change material, such as Germanium(Ge), Antimony(Sb), and Tellurium(Te) with composition Ge₂Sb₂Te₅, (GST-225) or GeSbTe-like materials including compositions of Indium (In), Tin (Sn), or Selenium (Se). The phase change material can be programmed into a high resistance amorphous state or a low resistance crystalline state by applying a short and high voltage pulse or a long and low voltage pulse, respectively. The reversible resistive device can be a Resistive RAM (RRAM) with cells fabricated from metal oxides between electrodes, such as Pt/NiO/Pt, TiN/TiOx/HfO2/TiN, TiN/ZnO/Pt. The resistance states can be changed reversibly and determined by polarity, magnitude, duration, or voltage/current-limit of pulse(s) to generate or annihilate conductive filaments. Another programmable resistive device similar to RRAM is a Conductive Bridge RAM (CBRAM) that is based on electro-chemical deposition and removal of metal ions in a thin solid-state electrolyte film. The electrodes can be oxidizable anode and an inert cathode and the electrolyte can be Ag- or Cu-doped chalcogenide glass such as GeSe or GeS, etc. The resistance states can be changed reversibly and determined by polarity, magnitude, duration, or voltage/current-limit of pulse(s) to generate or annihilate conductive bridges. The programmable resistive device can be an MRAM (Magnetic RAM) with cells fabricated from magnetic multi-layer stacks that construct a Magnetic Tunnel Junction (MTJ). In a Spin Transfer Torque MRAM (STT-MRAM) the direction of currents applied to a MTJ determines parallel or anti-parallel states, and hence low or high resistance states.

A conventional programmable resistive memory cell is shown in FIG. 1. The cell 10 consists of a resistive element 11 and an NMOS program selector 12. The resistive element 11 is coupled to the drain of the NMOS 12 at one end, and to a positive voltage V+ at the other end. The gate of the NMOS 12 is coupled to a select signal (Sel), and the source is coupled to a negative voltage V−. When a high voltage is applied to V+ and a low voltage to V−, the resistive device 10 can be programmed by raising the select signal (Sel) to turn on the NMOS 12. One of the most common resistive elements is a silicided polysilicon, the same material and fabricated at the same time as a MOS gate. The size of the NMOS 12, as program selector, needs to be larger enough to deliver the required program current for a few microseconds. The program current for a silicided polysilicon is normally between a few milliamps for a fuse with width of 40 nm to about 20 mA for a fuse with width about 0.6 um. As a result, the cell size of an electrical fuse using silicided polysilicon tends to be very large.

Another conventional programmable resistive device 20 for Phase Change Memory (PCM) is shown in FIG. 2( a). The PCM cell 20 has a phase change film 21 and a bipolar transistor 22 as program selector with P+ emitter 23, N base 27, and P-sub collector 25. The phase change film 21 is coupled to the emitter 23 of the bipolar transistor 22 in a ring shape, and to a positive voltage V+ at the other. The N type base 27 of bipolar transistor 22 is coupled to a negative voltage V−. The collector 25 is coupled to ground. By applying a proper voltage between V+ and V− for a proper duration of time, the phase change film 21 can be programmed into high or low resistance states, depending on voltage and duration. Conventionally, to program a phase-change memory to a high resistance state (or reset state) requires about 3V for 50 ns and consumes about 300 uA of current, or to program a phase-change memory to a low resistance state (or set state) requires about 2V for 300 ns and consumes about 100 uA of current.

FIG. 2( b) shows a cross section of a conventional bipolar transistor 22. The bipolar transistor 22 includes a P+ active region 23, a shallow N well 24, an N+ active region 27, a P-type substrate 25, and a Shallow Trench Isolation (STI) 26 for device isolation. The P+ active region 23 and N+ active region 27 coupled to the N well 24 are the P and N terminals of the emitter-base diode of the bipolar transistor 22, while the P− substrate 25 is the collector of the bipolar transistor 22. This cell configuration requires an N well 24 be shallower than the STI 26 to properly isolate cells from each other and needs 3-4 more masking operations over the standard CMOS logic processes which makes it more costly to fabricate.

Another programmable resistive device 20′ for Phase Change Memory (PCM) is shown in FIG. 2( c). The PCM cell 20′ has a phase change film 21′ and a diode 22′. The phase change film 21′ is coupled between an anode of the diode 22′ and a positive voltage V+. A cathode of the diode 22′ is coupled to a negative voltage V−. By applying a proper voltage between V+ and V− for a proper duration of time, the phase change film 21′ can be programmed into high or low resistance states, depending on voltage and duration. As an example of use of a diode as program selector for each PCM cell as shown in FIG. 2( c), see Kwang-Jin Lee et al., “A 90 nm 1.8V 512 Mb Diode-Switch PRAM with 266 MB/s Read Throughput,” International Solid-State Circuit Conference, 2007, pp. 472-273. Though this technology can reduce the PCM cell size to only 6.8 F² (F stands for feature size), the diode requires very complicated process steps, such as Selective Epitaxial Growth (SEG), to fabricate, which would be very costly for embedded PCM applications.

FIGS. 3( a) and 3(b) show several embodiments of an electrical fuse element 80 and 84, respectively, fabricated from an interconnect. The interconnect serves as a particular type of resistive element. The resistive element has three parts: anode, cathode, and body. The anode and cathode provide contacts for the resistive element to be connected to other parts of circuits so that a current can flow from the anode to cathode through the body. The body width determines the current density and hence the electro-migration threshold for a program current. FIG. 3( a) shows a conventional electrical fuse element 80 with an anode 81, a cathode 82, and a body 83. This embodiment has a large symmetrical anode and cathode. FIG. 3( b) shows another conventional electrical fuse element 84 with an anode 85, a cathode 86, and a body 87. This embodiment has an asymmetrical shape with a large anode and a small cathode to enhance the electro-migration effect based on polarity and reservoir effects. The polarity effect means that the electro-migration always starts from the cathode. The reservoir effect means that a smaller cathode makes electro-migration easier because the smaller area has lesser ions to replenish voids when the electro-migration occurs. The fuse elements 80, 84 in FIGS. 3( a) and 3(b) are relatively large structures which makes them unsuitable for some applications.

FIGS. 4( a) and 4(b) show programming a conventional MRAM cell 210 into parallel (or state 0) and anti-parallel (or state 1) by current directions. The MRAM cell 210 consists of a Magnetic Tunnel Junction (MTJ) 211 and an NMOS program selector 218. The MTJ 211 has multiple layers of ferromagnetic or anti-ferromagnetic stacks with metal oxide, such as Al₂O₃ or MgO, as an insulator in between. The MTJ 211 includes a free layer stack 212 on top and a fixed layer stack 213 underneath. By applying a proper current to the MTJ 211 with the program selector CMOS 218 turned on, the free layer stack 212 can be aligned into parallel or anti-parallel to the fixed layer stack 213 depending on the current flowing into or out of the fixed layer stack 213, respectively. Thus, the magnetic states can be programmed and the resultant states can be determined by resistance values, lower resistance for parallel and higher resistance for anti-parallel states. The resistances in state 0 or 1 are about 5KΩ or 10KΩ, respectively, and the program currents are about +/−100-200 μA. As an example of programming an MRAM cell see T. Kawahara, “2 Mb Spin-Transfer Torque RAM with Bit-by-Bit Bidirectional Current Write and Parallelizing-Direction Current Read,” International Solid-State Circuit Conference, 2007, pp. 480-481.

A diode can also be fabricated from polysilicon. FIG. 5( a) shows a cross section of a polysilicon diode. To form the polysilicon diode, the polysilicon is implanted by N+ at one end and P+ at the other end with a spacing Lc in between that has intrinsic doping level. The intrinsic doping level only means not intentionally doping any dopants but can be slightly N-type or P-type due to out diffusion or contamination. A silicide block layer is applied to block silicide formation on the surface of the polysilicon to thus prevent a short circuit. The two ends of P+ and N+ in polysilicon are further brought out as P and N terminals of a diode with contacts. As an example of a polysilicon diode see Ming-Dou Ker et al., “Ultra High-Voltage Charge Pump Circuit in Low-Voltage Bulk CMOS Processes with Polysilicon Diodes,” IEEE Transaction of Circuit and System-II, Vol. 54, No. 1, Jan. 2007, pp. 47-51.

FIG. 5( b) shows current verses voltage characteristics of a polysilicon diode, such as shown in FIG. 5( a). The current verses voltage curves show useful diode behavior such as a threshold voltage of about 0.6V and a leakage current of less than 1 nA. By varying the spacing Lc, the breakdown voltage and leakage current for the polysilicon diode can be adjusted accordingly.

SUMMARY OF THE INVENTION

Embodiments of programmable resistive device cells using polysilicon diodes as program selectors are disclosed. The programmable resistive devices can be fabricated using standard CMOS logic processes to reduce cell size and cost.

In one embodiment, a programmable resistive device and memory can use diodes fabricated on a polysilicon as program selectors, where the P and N terminals of the diode are P+ and N+ implants on the same polysilicon. The same P+ and N+ implants are used to create sources or drains of core logic PMOS and NMOS devices, respectively. Advantageously, the same polysilicon can be used to create CMOS gates in standard CMOS logic processes. By using polysilicon diodes in standard CMOS processes, a small cell size can be achieved, without incurring any special processing or masks. Thus, costs can be reduced substantially for variously applications, such as embedded applications.

According to one embodiment, a sensing circuit for programmable resistive device can use a diode as program selector. The sensing circuit can have a supply voltage VDDR of ˜2-3V, higher than ˜1.0V supply voltage for core logic devices. The sensing circuit can have a reference and a sensing branch. In one embodiment, each branch can have a first type of MOS with the source coupled to a first supply voltage, the drain coupled to the drain of a second type of MOS, which can have the gate coupled to a bias supply voltage. The sources of the second type of MOS in the reference and sensing branches can be coupled to a reference resistor and a programmable resistance element, respectively, and they are further coupled to a second supply voltage through their diodes. The gate of the first type of MOS in the sensing branch can be coupled to the gate of the first type of MOS in the reference branch, which can have the drain coupled to the gate. The resistance difference between the reference resistor and the programmable resistive element can be sensed through the drain of the first type of MOS in the sensing branch into a logic level.

The invention can be implemented in numerous ways, including as a method, system, device, or apparatus (including graphical user interface and computer readable medium). Several embodiments of the invention are discussed below.

Other aspects and advantages of the invention will become apparent from the following detailed description taken in conjunction with the accompanying drawings which illustrate, by way of example, the principles of the invention.

BRIEF DESCRIPTION OF THE DRAWINGS

The present invention will be readily understood by the following detailed descriptions in conjunction with the accompanying drawings, wherein like reference numerals designate like structural elements, and in which:

FIG. 1 shows a conventional programmable resistive memory cell.

FIG. 2( a) shows another conventional programmable resistive device for Phase Change Memory (PCM) using bipolar transistor as program selector.

FIG. 2( b) shows a cross section of a conventional Phase Change Memory (PCM) using bipolar transistor as program selector.

FIG. 2( c) shows another conventional Phase Change Memory (PCM) cell using diode as program selector.

FIGS. 3( a) and 3(b) show several embodiments of an electrical fuse element, respectively, fabricated from an interconnect.

FIGS. 4( a) and 4(b) show programming a conventional MRAM cell into parallel (or state 0) and anti-parallel (or state 1) by current directions.

FIG. 5( a) shows a cross section of a polysilicon diode.

FIG. 5( b) shows current verses voltage characteristics of a polysilicon diode, such as shown in FIG. 5( a).

FIG. 6( a) shows a block diagram of a memory cell using a polysilicon diode as program selector according to one embodiment.

FIG. 6( b) shows a top view of a fuse cell using a polysilicon diode as program selector according to one embodiment.

FIG. 7( a) shows an electrical fuse element according to one embodiment.

FIGS. 7( b), (c), and (d) show a top view of electrical fuse cells using polysilicon as fuse elements and polysilicon diodes according to various embodiments.

FIG. 8( a) shows a top view of a polysilicon electrical fuse cell having a common P terminal as anode shared by 4 polysilicon diodes with four fuse elements in accordance with one embodiment.

FIG. 8( b) shows a top view of a 4×6 array of via1 fuses built on polysilicon in accordance with one embodiment.

FIG. 8( c) shows a top view of an array of polysilicon fuses with a diode constructed from a P+ polysilicon and an N type buried layer at cross points according to one embodiment.

FIG. 9( a) shows a cross section of a programmable resistive device cell using phase-change material as a resistive element, with buffer metals and a polysilicon diode, according to one embodiment.

FIG. 9( b) shows a top view of a PCM cell with a polysilicon diode as program selector having a cell boundary in accordance with one embodiment.

FIG. 10 shows one embodiment of an MRAM cell using diodes as program selectors in accordance with one embodiment.

FIG. 11( a) shows a top view of an MRAM cell with an MTJ as a resistive element and with polysilicon diodes and as program selectors in accordance with one embodiment.

FIG. 11( b) shows another top view of a MRAM cell with the MTJ as a resistive element and with the polysilicon diodes as program selectors in accordance with another embodiment.

FIG. 11( c) shows another top view of a MRAM cell by using one polysilicon diode and one junction diode in accordance with one embodiment.

FIG. 11( d) shows another top view of a MRAM cell by using one polysilicon diode and one junction diode with an abutted contact in accordance with another embodiment.

FIG. 12( a) shows one embodiment of a three-terminal 2×2 MRAM cell array using diodes as program selectors and the condition to program the upper-right cell into 1 in accordance with one embodiment.

FIG. 12( b) shows alternative conditions to program the upper-right cell into 1 in a 2×2 MRAM array in accordance with one embodiment.

FIG. 13( a) shows one embodiment of a three-terminal 2×2 MRAM cell array using diodes as program selectors and the condition to program the upper-right cell into 0 in accordance with one embodiment.

FIG. 13( b) shows alternative conditions to program the upper-right cell into 0 in a 2×2 MRAM array in accordance with one embodiment.

FIGS. 14( a) and 14(b) show one embodiment of programming 1 and 0 into the upper-right cell, respectively, in a two-terminal 2×2 MRAM cell array in accordance with one embodiment.

FIG. 15 shows a portion of a programmable resistive memory constructed by an array of n-row by (m+1)-column non-MRAM type of cells and n wordline drivers in accordance with one embodiment.

FIG. 16( a) shows a portion of a programmable resistive memory constructed by an array of 3-terminal MRAM cells according to one embodiment.

FIG. 16( b) shows another embodiment of constructing a portion of MRAM memory with 2-terminal MRAM cells.

FIGS. 17( a), 17(b), and 17(c) show three other embodiments of constructing reference cells for differential sensing.

FIG. 18( a) shows a schematic of a wordline driver circuit according to one embodiment.

FIG. 18( b) shows a schematic of a bitline circuit according to one embodiment.

FIG. 18( c) shows a portion of memory with an internal power supply VDDP coupled to an external supply VDDPP and a core logic supply VDD through power selectors.

FIG. 19( a) shows one embodiment of a schematic of a pre-amplifier according to one embodiment.

FIG. 19( b) shows one embodiment of a schematic of an amplifier according to one embodiment.

FIG. 19( c) shows a timing diagram of the pre-amplifier and the amplifier in FIGS. 19( a) and 19(b), respectively.

FIG. 20( a) shows another embodiment of a pre-amplifier, similar to the pre-amplifier in FIG. 18( a).

FIG. 20( b) shows level shifters according to one embodiment.

FIG. 20( c) shows another embodiment of an amplifier with current-mirror loads.

FIG. 20( d) shows another embodiment of a pre-amplifier with two levels of PMOS pullup stacked so that all core devices can be used.

FIG. 20( e) shows another embodiment of a pre-amplifier with an activation device for enabling.

FIG. 21( a) depicts a method of programming a programmable resistive memory in a flow chart according to one embodiment.

FIG. 21( b) depicts a method of reading a programmable resistive memory in a flow chart according to one embodiment.

FIG. 22 shows a processor system according to one embodiment.

DETAILED DESCRIPTION OF EMBODIMENTS OF THE INVENTION

Embodiments disclosed herein use a polysilicon diode as program selector for a programmable resistive device. The diode can comprise P+ and N+ implants on a polysilicon substrate. Since the P+ and N+ implants and polysilicon are readily available in standard CMOS logic processes, these devices can be formed in an efficient and cost effective manner. There are no additional masks or process steps to save costs. The programmable resistive device can also be included within an electronic system.

According to one embodiment, a sensing circuit for programmable resistive device can use a diode as program selector. The sensing circuit can have a supply voltage VDDR of ˜2-3V, higher than ˜1.0V supply voltage for core logic devices. The sensing circuit can have a reference and a sensing branch. In one embodiment, each branch can have a first type of MOS with the source coupled to a first supply voltage, the drain coupled to the drain of a second type of MOS, which can have the gate coupled to a bias supply voltage. The sources of the second type of MOS in the reference and sensing branches can be coupled to a reference resistor and a programmable resistance element, respectively, and they are further coupled to a second supply voltage through their diodes. The gate of the first type of MOS in the sensing branch can be coupled to the gate of the first type of MOS in the reference branch, which can have the drain coupled to the gate. The resistance difference between the reference resistor and the programmable resistive element can be sensed through the drain of the first type of MOS in the sensing branch into a logic level.

FIG. 6( a) shows a block diagram of a memory cell 30 using a polysilicon diode according to the present invention. In particular, the memory cell 30 includes a resistive element 31 and a polysilicon diode 32. The resistive element 31 can be coupled between an anode of the polysilicon diode 32 and a positive voltage V+. A cathode of the polysilicon diode 32 can be coupled to a negative voltage V−. In one implementation, the memory cell 30 can be a fuse cell with the resistive element 31 operating as an electrical fuse. The polysilicon diode 32 can serve as a program selector. The coupling of the resistive element 31 and the polysilicon diode 32 between the supply voltages V+ and V− can be interchanged. By applying a proper voltage between V+ and V− for a proper duration of time, the resistive element 31 can be programmed into high or low resistance states, depending on voltage and duration, thereby programming the memory cell 30 to store a data value (e.g., bit of data).

FIG. 6( b) shows a top view of a fuse cell 30 using a polysilicon diode as program selector according to one embodiment. The fuse cell 30 include an electrical fuse element 31 coupled to a first supply voltage V+ and to a diode 32. The diode 32 serves as the program selector for the fuse cell 30. The diode 32 is built on a piece of polysilicon 34, i.e., polysilicon substrate. The P+ and N+ implants 33 and 37 are used to create source or drain of a PMOS or NMOS device, respectively, and thus form the P and N terminals of the diode 32 on the polysilicon 34. A Silicide Block Layer (SBL) 36 blocks silicide formation on the top of polysilicon surface to prevent P and N terminals of the diode 32 from shorting. A space d between P+ 33 and N+ 37 can be used to adjust breakdown voltage and leakage current. A layer 39 is optional to introduce NLDD, PLDD, NMOS Vt, PMOS Vt or others implants over the intrinsic dopant level into the area between N+ and P+ implant layers 37 and 33 to further control the diode's turn-on resistance. The area implanted by the optional layers 39 can be generated from standard CMOS masks by operations on layer database without any additional costs.

FIG. 7( a) shows an electrical fuse element 88 according to one embodiment. The electrical fuse element 88 can, for example, by used as the electrical fuse element 31 illustrated in FIGS. 6( a) and 6(b). The electrical fuse element 88 includes an anode 89, a cathode 90, and a body 91. In this embodiment, the electrical fuse element 88 is a bar shape with a small anode 89 and cathode 90 to reduce area. The anode 89 and cathode 90 may protrude from the body 91 to make contacts. The contact number can be one (1) for both the anode 89 and the cathode 90 so that the area can be very small. However, the contact area for anode 89 is often made larger so that the anode 89 can resist electro-migration more than the cathode 90. The fuse body 91 can have about 1-5 squares, namely, the length to width ratio is about 1-to-5, to optimize cell area and program current. The fuse element 88 has a P+ implant 92 covering part of the body 91 and the cathode 90, while an N+ implant over the rest of area. This embodiment makes the fuse element 88 behaves like a reverse biased diode to increase resistance after being programmed, when the silicide on top is depleted by electro-migration, ion diffusion, silicide decomposition, and other effects.

The above scheme can be realized for those fuse elements consisting of polysilicon, silicided polysilicon, thermally isolated active region, local interconnect (LI), or other CMOS gate. Particularly, some fuse elements allows P+ and N+ implants creating a diode after being programmed, such as polysilicon, thermally isolated active region, or gate of a metal-gate CMOS. For example, if a metal-gate CMOS has a sandwich structure of polysilicon between metal alloy layers, the metal alloy layers may be blocked by masks generated from the layout database to create a diode on the fuse element. In SOI or SOI-like processes, a fuse element can also be constructed from a thermally isolated active region such that the fuse element can be implanted with N+, P+, or N+ and P+ in each end of the active region. If a fuse element is partly implanted with N+ and P+, the fuse element can behave like a reverse-biased diode when the silicide on top is depleted after being programmed. In some processing technologies that can offer Local Interconnect, a by-product in salicide processes that has capability to interconnect polysilicon and active region directly, the fuse element can be constructed from part or all of a local interconnect. Furthermore, the fuse element and one terminal of the program-selector diode can be connected with a butted contact to save area. There are many variations in constructing electrical fuse elements in CMOS processes, those skilled in the art understand that the above discussions are for illustration purposes. The variations and their combinations can be used with various embodiments.

FIGS. 7( b), 7(c), and 7(d) show a top view of electrical fuse cells using polysilicon as fuse elements and polysilicon diodes according to various embodiments. Since the fuse element is fabricated from a polysilicon and the diode is built on a polysilicon substrate, the fuse element and the diode can be integrally formed. By integrally forming the fuse element and the diode, programmable resistive cells that are compact can be formed because redundant contacts and spacing can be avoided.

FIG. 7( b) shows a one-piece polysilicon electrical fuse cell 80 having a fuse element with anode 89, body 87, and a polysilicon diode 81 according to one embodiment. The anode 89, the body 87 and a P terminal of the polysilicon diode 81 are covered by a P+ implant 83, while the cathode 88 (the N terminal of the polysilicon diode 81) is covered by an N+ implant 84. Silicide Block Layer 82 can be provided over at least adjacent portions of the P+ implant 83 and the N+ implant 84 to block silicide grown on the top of polysilicon to prevent N and P terminals from shorting. The anode 89 is coupled to V+ and the cathode 88 is coupled to V−. When a high voltage is applied to V+ and a low voltage to V−, a current flows from the anode 89 through body 87 to the P terminal of the polysilicon diode 81 and then to the N terminal 88 of the polysilicon diode 81. In this embodiment, the body 87 of fuse element has a P+ implant 83.

FIG. 7( c) shows another one-piece polysilicon electrical fuse cell 90 having a diode 91 and a fuse element with a body 97 and a cathode 99 according to one embodiment. The P terminal of the diode 91 is coupled to a supply voltage V+. The N terminal of the diode 91 is coupled to the body 97 of the fuse element, which is then coupled to another supply voltage V− through the cathode 99. The P terminal 98 of the diode 91, lower half of the body 97, and the cathode 99 are covered by a P+ implant 93, while the N terminal of the diode 91 and the upper portion (e.g., half) of the body 97 are covered by an N+ implant 94. A silicide Block Layer 92 can block silicide grown on top of polysilicon to prevent the N and P terminals from shorting. When a high voltage is applied to V+ and a low voltage to V−, a current flows from the P terminal 98 of the polysilicon diode 91 through the N terminal of the polysilicon diode 91 and the body 97 to the cathode 99. In this embodiment, the body 97 has N+/P+ implants covering respective portions (e.g., approximately half N+ and half P+). When the silicide on the top of the polysilicon diode 91 is depleted, the body 97 behaves like a reverse biased diode to increase the post-program resistance. Besides, the cathode 99 has a smaller area than the anode, i.e., the P terminal 98 of the polysilicon diode 91, which serves to enhance electro-migration.

FIG. 7( d) shows a top view of a pair of staggered one-piece electrical fuse cells according to one embodiment. Like the polysilicon electrical fuse cell 90, each of the electrical fuse cells in the pair are formed of a polysilicon resistive element (e.g., fuse element) and a polysilicon diode. The second electrical fuse cell is rotated 180-degrees and placed adjacent the first electrical fuse cell so that the large anode and small cathode are adjacent next to each other for a compact (or dense) arrangement that consumed a relatively small area.

If the program current is not very high, the size of the one-piece electrical fuse cells can be further reduced. FIG. 8( a) shows a top view of a polysilicon electrical fuse cell 91 having a common P terminal 98 (implanted by P+ 93) as anode shared by 4 polysilicon diodes 96 for use with four fuse elements 95 in accordance with one embodiment. The SBL 92 blocks silicide formation on the top of the polysilicon diode 96 to separate P terminal 98 and N terminal of diodes 96 for each electrical fuse cell. A polysilicon diode 96 which serves as program selector is coupled to a portion of polysilicon covered by an N+ 94 as the N terminal, which is further coupled to a body 97 and to a cathode 99. The P terminal 98 is coupled to a high voltage supply V+ and each cathode 99 is coupled to a low voltage supply V−. By applying proper voltages to V+ and V−, a current will flow to change the resistance of the body 97 accordingly.

FIG. 8( b) shows a top view of a 4×6 array of via1 fuses 90 built on polysilicon in accordance with one embodiment. The array of via1 fuses 90 has four rows of polysilicon diode 91, each has alternative N+ contacts 97 and P+ contacts 99 covered by N+ implant 94 and P+ implant 93, respectively, with metal1 on top. The P+ contacts 99 and N+ contacts 97, which are separated by a SBL 92 act as the P and N terminals of diodes. The N+ contacts 97 in the same columns are connected by a metal2 running vertically as wordlines. Similarly, the P+ contacts 99 in the same rows are connected by a metal3 running horizontally as bitlines. A particular programmable resistive cell 96 can be programmed by applying a high voltage to a selected bitline and a low voltage or ground to a selected wordline to conduct a current flowing from metal3 bitline, via1, metal2, contact, polysilicon, through the selected diode and metal1 to ground. If the metal1, metal2, and metal3 have higher threshold to blow up, either via1 (connect between metal1 and metal2) or contact (connect between metal1 and polysilicon) will be programmed. To ensure via1 being programmed, the metals are preferably made wider and the numbers of via2 and contacts are preferably more than one. In one embodiment, the via1 can be built on the top of a P+ contact 99 to make a unit cell very small. Those skilled in the art understand that in other embodiments the via1 fuses can be extended to contact. via2, various other types of contact/via fuses or metal schemes may be used, and the numbers of rows and column may vary, the rows and columns are interchangeable.

FIG. 8( c) shows a top view 60 of a 4×6 array of polysilicon fuses with a diode constructed from a P+ polysilicon 61 and an N type buried layer 62 at cross points according to one embodiment. The buried layer 62 is an active region with an implant before the N+ or P+ implants 64 and 63 for sources or drains of CMOS. Therefore, the buried layer 62 can be used as an interconnect underneath and can be crossed by the P+ polysilicon 61 provided above. In this embodiment, the buried layer 62 is implanted with an N-type dopant before active-region isolations are fabricated. The gate oxide grown on top of the buried layer 62 is stripped before the P+ polysilicon 61 is deposited. The polysilicon is partly implanted by a P-type dopant as the P terminal of a diode, and partly implanted by an N-type dopant as an N-type polysilicon fuse, though a silicide on top connects the two parts. As a result, a very compact P/N polysilicon fuse with a P-type polysilicon and N-type bulk silicon as two terminals of a diode is constructed. Metal 2 straps the buried layer 62, (not shown in FIG. 8( c)), running in the vertical direction as a wordline, and metal 3 straps the polysilicon through contacts 65 running in the horizontal direction as a bitline.

FIG. 9( a) shows a cross section of a programmable resistive device cell 50 using phase-change material as a resistive element 42, with buffer metals 41 and 43, and a polysilicon diode 30 on a silicon substrate with a dielectric 49, according to one embodiment. The polysilicon diode 30 has a P+ implant 33 and N+ implant 37 on a polysilicon substrate 31 as P and N terminals through anode contact 32 and cathode contact 39. A SBL 35 separates the P+ implant 33 from the N+ implant 37. The anode 32 of the polysilicon diode 30 is coupled to a lower metal 41 as a buffer layer through a contact plug 40-1. The lower metal 41 is then coupled to a thin film of phase-change material 42 (e.g., PCM film) and an upper metal buffer layer 43 through a contact plug 40-2. The upper metal is coupled to another metal 44 to act as a bitline (BL) through a plug 40-3. The PCM film 42 can have a chemical composition of Germanium (Ge), Antimony (Sb), and/or Tellurium (Te), such as Ge_(x)Sb_(y)Te_(z) (x,y, and z are any arbitrary numbers) or, more particularly, Ge₂Sb₂Te₅.(GST-225). The PCM film 42 can be doped with at least one or more of Indium (In), Tin (Sn), or Selenium (Se) to enhance performance. The PCM structure can be substantially planar, which means the PCM film area is larger than the film contact area coupled to the program selector (polysilicon diode 30), or the height from the surface of the silicon substrate to the film is much smaller than the dimensions of the film parallel to silicon substrate. In this embodiment, the active area of PCM film 42 (e.g., GST film) is much larger than the contact area so that the programming characteristics can be more uniform and reproducible. The GST film 42 is not a vertical structure and does not sit on top of a tall contact, which is more suitable for embedded PCM applications, especially when the polysilicon diode 30 is used as program selector to make the cell size very small. For those skilled in the art understand that the structure and fabrication processes may vary and that the structures of GST film and buffer metals described above are for illustrative purpose.

FIG. 9( b) shows a top view of a PCM cell using a polysilicon diode as program selector with a cell boundary 70 in accordance with one embodiment. The PCM cell has a polysilicon diode 71 and a phase-change material 75. The polysilicon diode 71 has an anode 72 and a cathode 79 covered by P+ and N+ implants 73 and 77, respectively. A SBL 80 blocks silicide formation on the top of polysilicon diode 71 to prevent the anode 72 from shorting to the cathode 79. The anode 72 is coupled to the phase-change film 75 through a metal1 76. The phase-change film 75 is further coupled to a metal3 bitline (BL) 78 running vertically. The cathode 79 of the polysilicon diode 71 is connected by a metal2 wordline (WL) 77 running horizontally. By applying a proper voltage between the bitline 78 and the wordline 77 for a suitable duration, the phase-change film can be programmed into a 0 or 1 state accordingly. Since programming the phase-change film is based on raising the temperature rather than electro-migration as with an electrical fuse, the phase-change film (e.g., GST film) can be symmetrical in area for both anode and cathode. Those skilled in the art understand that the phase-change film, structure, layout style, and metal schemes may vary and that the above description is for illustrative purpose.

Programming a phase-change memory, such as a phase-change film, depends on the physical properties of the phase-change film, such as glass transition and melting temperatures. To reset, the phase-change film needs to be heated up beyond the melting temperature and then quenched. To set, the phase-change film needs to be heated up between melting and glass transition temperatures and then annealed. A typical phase-change film has glass transition temperature of about 200° C. and melting temperature of about 600° C. These temperatures determine the operation temperature of a phase-change memory because the resistance state may change after staying in a particular temperature for a long time. However, most applications require retaining data for 10 years for the operation temperature from 0 to 85° C. or even from −40 to 125° C. To maintain cell stability over the device's lifetime and over such a wide temperature range, periodic reading and then writing back data into the same cells can be performed. The refresh period can be quite long, e.g., longer than a second, such as days, weeks, or even months. The refresh mechanism can be generated inside the memory or triggered from outside the memory. The long refresh mechanism can serve to maintain cell stability be applied to other emerging memories such as RRAM, CBRAM, and MRAM, etc.

FIG. 10 shows one embodiment of an MRAM cell 310 using diodes 317 and 318 as program selectors in accordance with one embodiment. The MRAM cell 310 in FIG. 10 is a three-terminal MRAM cell. The MRAM cell 310 has an MTJ 311, including a free layer stack 312 and a fixed layer stack 313 with a dielectric film in between, and the two diodes 317 and 318. The free layer stack 312 is coupled to a supply voltage V, and coupled to the fixed layer stack 313 through a metal oxide such as Al₂O₃ or MgO. The diode 317 has the N terminal coupled to the fixed layer stack 313 and the P terminal coupled to V+ for programming a 1. The diode 318 has the P terminal coupled to the fixed layer stack 313 and the N terminal coupled to V− for programming a 0. If V+ voltage is higher than V, a current flows from V+ to V to program the MTJ 311 into state 1. Similarly, if V− voltage is lower than V, a current flows from V to V− to program the MTJ 311 into state 0. During programming, the other diode is supposedly cutoff. For reading, V+ and V− can be both set to 0V and the resistance between node V and V+/V− can be sensed to determine whether the MTJ 311 is in state 0 or 1.

FIG. 11( a) shows a top view of an MRAM cell 80 with an MTJ 89 as a resistive element and with polysilicon diodes 86 and 88 as program selectors in accordance with one embodiment. The MTJ 89 has a slant ellipse shape with a free layer stack on top, a fixed layer stack underneath, and a dielectric in between to constitute a magnetic tunneling junction. The MTJ 89 is coupled to a metal3 bitline on top running vertically. Program-1 diode 86 and program-0 diode 88 are polysilicon diodes built on two sections (e.g., rectangles) of polysilicon 81 and are placed side by side and connected at one end, i.e., the N terminal of the diode 86 is connected to the P terminal of the diode 88. A P+ implant 83 and an N+ implant 87 define the P and N terminals of the diodes 86 and 88. A SBL 82 can be provided to prevent shorting. The program-1 diode 86 has the P terminal coupled to a supply voltage V+ and has the N terminal coupled to the fixed stack of MTJ 89. The program-0 diode 88 has the N terminal coupled to a supply voltage V− and has the P terminal coupled to the fixed stack of MTJ 89. The V+ and V− voltages of each MRAM cell 80 are connected as metal2 wordlines, WLP and WLN, running horizontally.

FIG. 11( b) shows another top view of a MRAM cell 80′ with the MTJ 89 as a resistive element and with the polysilicon diodes 86 and 88 as program selectors in accordance with another embodiment. The MTJ 89 has a slant ellipse shape with a free layer stack on top, a fixed layer stack underneath, and a dielectric in between to constitute a magnetic tunneling junction. The MTJ 89 is coupled to a metal3 bitline on top running vertically. The Program-1 diode 86 and the program-0 diode 88 are connected back to back in a one-piece polysilicon section 81 (e.g., rectangle). Namely, the N terminal of the diode 86 is connected to the P terminal of the diode 88. A P+ implant 83 and an N+ implant 87 define the P and N terminals of the diodes 86 and 88. The SBL 82 has two sections provided to prevent shorting. The program-1 diode 86 has the P terminal coupled to a supply voltage V+ and the N terminal coupled to the fixed stack of MTJ 89. The program-0 diode 88 has the N terminal coupled to a supply voltage V− and the P terminal coupled to the fixed stack of MTJ 89. The V+ and V− voltages of each MRAM cell 80′ are connected in metal2 wordlines, WLP and WLN, running horizontally. The top views shown in FIGS. 11( a) and (b) are for illustrative purposes and those skilled in the art understand that there are many ways of constructing polysilicion diodes coupled with a MTJ and metal schemes.

FIG. 11( c) shows another top view of a MRAM cell 80″ by using one polysilicon diode 88 and one junction diode 86′ in accordance with one embodiment. The P+ implant 83′ and N+ implant 87 define the P and the N terminals of diodes the 88 and 86′ over a polysilicon section 91 and an active region 92, respectively. The junction diode 86′ is housed in an N well for CMOS devices, and has the P terminal coupled to a supply voltage V+ and the N terminal coupled to the P terminal of the polysilicon diode 88 and then to another supply voltage V through the MTJ 89 and the metal1 93. A dummy CMOS gate 85 can separate the P and N terminals of the junction diode 86. Similarly, the polysilicon diode 88 has the N terminal coupled to a supply voltage V− and the P terminal coupled to the N terminal of the junction diode 86′ and to a supply voltage V through the MTJ 89 and the metal1 93. The SBL 82 separates the P and N terminals of the polysilicon diode 88. The supply voltage V is further coupled to a metal3 bitline running vertically, while the supply voltages V+ and V− are coupled to metal2 wordlines, WLP and WLN, running horizontally.

FIG. 11( d) shows another top view of a MRAM cell 80′″ by using one polysilicon diode 88 and one junction diode 86′ with an abutted contact 84 in accordance with another embodiment. The P+ implant 83′ and the N+ implant 87 define the P and N terminals of the diodes 88 and 86′ over a polysilicon section 91 and an active region 92, respectively. The junction diode 86′ is housed in an N well for CMOS devices, and has the P terminal coupled to a supply voltage V+ and the N terminal coupled to the P terminal of the polysilicon diode 88 and to another supply voltage V through the MTJ 89 and the metal1 93. The dummy CMOS gate 85 can separate the P and N terminals of the junction diode 86′. Similarly, the polysilicon diode 88 has the N terminal coupled to a supply voltage V− and the P terminal coupled to the N terminal of the junction diode 86′ and to a supply voltage V through the MTJ 89 and the metal1 93. The SBL 82 separates the P and N terminals of the polysilicon diode 88. The supply voltage V is further coupled to a metal3 bitline running vertically, while the supply voltage V+ and V− are coupled to metal2 wordlines, WLP and WLN, running horizontally. A contact to couple the N terminal of the junction diode 86′ and the P terminal of the polysilicon diode 88 is through an abutted contact 84. The polysilicon 91 overlaps into the action region 92 with a metal1 93 on top to connect polysilicon and active region in a single contact 84. Hence, two contacts are merged into one and thus polysilicon-to-active spacing can be saved to reduce area and costs, thereby rendering this embodiment particularly efficient. Using of junction diode and polysilicon diodes in FIGS. 11( c) and 11(d) as program-1 and program-0 diodes, respectively, can be interchangeable. Those skilled in the art understand that various embodiments of mixing different kinds of diodes in various configurations for memory are possible.

FIG. 12( a) shows one embodiment of a three-terminal 2×2 MRAM cell array using diodes 317 and 318 as program selectors and the condition to program 1 in a cell in accordance with one embodiment. Cells 310-00, 310-01, 310-10, and 310-11 are organized as a two-dimensional array. The cell 310-00 has a MTJ 311-00, a program-1 diode 317-00, and a program-0 diode 318-00. The MTJ 311-00 is coupled to a supply voltage V at one end, to the N terminal of the program-1 diode 317-00 and to the P terminal of the program-0 diode 318-00 at the other end. The P terminal of the program-1 diode 317-00 is coupled to a supply voltage V+. The N terminal of the program-0 diode 318-00 is coupled to another supply voltage V−. The other cells 310-01, 310-10, and 310-11 are similarly coupled. The voltage Vs of the cells 310-00 and 310-10 in the same columns are connected to BL0. The voltage Vs of the cells 310-01 and 310-11 in the same column are connected to BL1. The voltages V+ and V− of the cells 310-00 and 310-01 in the same row are connected to WL0P and WL0N, respectively. The voltages V+ and V− of the cells 310-10 and 310-11 in the same row are connected to WL1P and WL1N, respectively. To program a 1 into the cell 310-01, WL0P is set high and BL1 is set low, while setting the other BL and WLs at proper voltages as shown in FIG. 12( a) to disable the other program-1 and program-0 diodes. The bold line in FIG. 12( a) shows the direction of current flow.

FIG. 12( b) shows alternative program-1 conditions for the cell 310-01 in a 2×2 MRAM array in accordance with one embodiment. For example, to program a 1 into cell 310-01, set BL1 and WL0P to low and high, respectively. If BL0 is set to high in condition 1, the WL0N and WL1N can be either high or floating, and WL1P can be either low or floating. The high and low voltages of an MRAM in today's technologies are about 2-3V for high voltage and 0 for low voltage, respectively. If BL0 is floating in condition 2, WL0N and WL1N can be high, low, or floating, and WL1P can be either low or floating. In a practical implementation, the floating nodes are usually coupled to very weak devices to a fixed voltage to prevent leakage. One embodiment of the program-1 condition is shown in FIG. 12( a) without any nodes floating.

FIG. 13( a) shows one embodiment of a three-terminal 2×2 MRAM cell array with MTJ 311 and diodes 317 and 318 as program selectors and the condition to program 0 in a cell in accordance with one embodiment. The cells 310-00, 310-01, 310-10, and 310-11 are organized as a two-dimensional array. The cell 310-00 has a MTJ 311-00, a program-1 diode 317-00, and a program-0 diode 318-00. The MTJ 311-00 is coupled to a supply voltage V at one end, to the N terminal of program-1 diode 317-00 and to the P terminal of program-0 diode 318-00 at the other end. The P terminal of the program-1 diode 317-00 is coupled to a supply voltage V+. The N terminal of the program-0 diode 318-00 is coupled to another supply voltage V−. The other cells 310-01, 310-10, and 310-11 are similarly coupled. The voltage Vs of the cells 310-00 and 310-10 in the same columns are connected to BL0. The voltage Vs of the cells 310-01 and 310-11 in the same column are connected to BL1. The voltages V+ and V− of the cells 310-00 and 310-01 in the same row are connected to WL0P and WL0N, respectively. The voltages V+ and V− of the cells 310-10 and 310-11 in the same row are connected to WL1P and WL1N, respectively. To program a 0 into the cell 310-01, WL0N is set low and BL1 is set high, while setting the other BL and WLs at proper voltages as shown in FIG. 13( a) to disable the other program-1 and program-0 diodes. The bold line in FIG. 13( a) shows the direction of current flow.

FIG. 13( b) shows alternative program-0 conditions for the cell 310-01 in a 2×2 MRAM array in accordance with one embodiment. For example, to program a 0 into cell 310-01, set BL1 and WL0N to high and low, respectively. If BL0 is set to low in condition 1, the WL0P and WL1P can be either low or floating, and WL1N can be either high or floating. The high and low voltages of an MRAM in today's technologies are about 2-3V for high voltage and 0 for low voltage, respectively. If BL0 is floating in condition 2, WL0P and WL1P can be high, low, or floating, and WL1N can be either high or floating. In a practical implementation, the floating nodes are usually coupled to very weak devices to a fixed voltage to prevent leakage. One embodiment of the program-0 condition is as shown in FIG. 13( a) without any nodes floating.

The cells in 2×2 MRAM arrays in FIGS. 12( a), 12(b), 13(a) and 13(b) are three-terminal cells, namely, cells with V, V+, and V− nodes. However, if the program voltage VDDP is less than twice a diode's threshold voltage Vd, i.e. VDDP<2*Vd, the V+ and V− nodes of the same cell can be connected together as a two-terminal cell. Since Vd is about 0.6-0.7V at room temperature, this two-terminal cell works if the program high voltage is less than 1.2V and low voltage is 0V. This is a common voltage configuration of MRAM arrays for advanced CMOS technologies that has supply voltage of about 1.0V. FIGS. 14( a) and 14(b) show schematics for programming a 1 and 0, respectively, in a two-terminal 2×2 MRAM array.

FIGS. 14( a) and 14(b) show one embodiment of programming 1 and 0, respectively, in a two-terminal 2×2 MRAM cell array in accordance with one embodiment. The cells 310-00, 310-01, 310-10, and 310-11 are organized in a two-dimensional array. The cell 310-00 has the MTJ 311-00, the program-1 diode 317-00, and the program-0 diode 318-00. The MTJ 311-00 is coupled to a supply voltage V at one end, to the N terminal of program-1 diode 317-00 and the P terminal of program-0 diode 318-00 at the other end. The P terminal of the program-1 diode 317-00 is coupled to a supply voltage V+. The N terminal of the program-0 diode 318-00 is coupled to another supply voltage V−. The voltages V+ and V− are connected together in the cell level if VDDP<2*Vd can be met. The other cells 310-01, 310-10 and 310-11 are similarly coupled. The voltages Vs of the cells 310-00 and 310-10 in the same columns are connected to BL0. The voltage Vs of the cells 310-01 and 310-11 in the same column are connected to BL1. The voltages V+ and V− of the cells 310-00 and 310-01 in the same row are connected to WL0. The voltages V+ and V− of the cells 310-10 and 310-11 in the same row are connected to WL1.

To program a 1 into the cell 310-01, WL0 is set high and BL1 is set low, while setting the other BL and WLs at proper voltages as shown in FIG. 14( a) to disable other program-1 and program-0 diodes. The bold line in FIG. 14( a) shows the direction of current flow. To program a 0 into the cell 310-01, WL0 is set low and BL1 is set high, while setting the other BL and WLs at proper voltages as shown in FIG. 14( b) to disable the other program-1 and program-0 diodes. The bold line in FIG. 14( b) shows the direction of current flow.

The embodiments of constructing MRAM cells in a 2×2 array as shown in FIGS. 12( a)-14(b) are for illustrative purposes. Those skilled in the art understand that the number of cells, rows, or columns in a memory can be constructed arbitrarily and rows and columns are interchangeable.

The programmable resistive devices can be used to construct a memory in accordance with one embodiment. FIG. 15 shows a portion of a programmable resistive memory 100 constructed by an array 101 of n-row by (m+1)-column non-MRAM cells 110 and n wordline drivers 150-i, where i=0,1, . . . , n−1, in accordance with one embodiment. The memory array 101 has m normal columns and one reference column for one shared sense amplifier 140 for differential sensing. Each of the memory cells 110 has a resistive element 111 coupled to the P terminal of a diode 112 as program selector and to a bitline BLj 1701 (j=0,1, . . . m−1) or reference bitline BLR0 175-0 for those of the memory cells 110 in the same column. The N terminal of the diode 112 is coupled to a wordline WLBi 152-i through a local wordline LWLBi 154-i, where i=0,1, . . . , n−1, for those of the memory cells 110 in the same row. Each wordline WLBi is coupled to at least one local wordline LWLBi, where i=0,1, . . . , n−1. The LWLBi 154-i is generally constructed by a high resistivity material, such as N well or polysilicon, to connect cells, and then coupled to the WLBi (e.g., a low-resistivity metal WLBi) through conductive contacts or vias, buffers, or post-decoders 172-i, where i=0,1, . . . , n−1. Buffers or post-decoders 172-i may be needed when using diodes as program selectors because there are currents flowing through the WLBi, especially when one WLBi drives multiple cells for program or read simultaneously in other embodiments. The wordline WLBi is driven by the wordline driver 150-i with a supply voltage vddi that can be switched between different voltages for program and read. Each BLj 170-j or BLR0 175-0 is coupled to a supply voltage VDDP through a Y-write pass gate 120-j or 125 for programming, where each BLj 170-j or BLR0 175-0 is selected by YSWBj (j=0, 1, . . . , m−1) or YSWRB0, respectively. The Y-write pass gate 120-j (j=0,1, . . . , m−1) or 125 can be built by PMOS, though NMOS, diode, or bipolar devices can be employed in some embodiments. Each BL or BLR0 is coupled to a dataline DL or DLR0 through a Y-read pass gate 130-j or 135 selected by YSRj (j=0,1, . . . , m−1) or YSRR0, respectively. In this portion of memory array 101, m normal datalines DLj (j=0,1, . . . , m−1) are connected to an input 160 of a sense amplifier 140. The reference dataline DLR0 provides another input 161 for the sense amplifier 140 (no multiplex is generally needed in the reference branch). The output of the sense amplifiers 140 is Q0.

To program a cell, the specific WLBi and YSWBj are turned on and a high voltage is supplied to VDDP, where i=0,1, . . . n−1 and j=0,1, . . . , m−1. In some embodiments, the reference cells can be programmed to 0 or 1 by turning on WLRBi, and YSWRB0, where i=0,1, . . . , n−1. To read a cell, a data column 160 can be selected by turning on the specific WLBi and YSRj, where i=0,1, . . . , n−1, and j=0,1, . . . , m−1, and a reference cell coupled to the reference dataline DLR0 161 for the sense amplifier 140 can be selected to sense and compare the resistance difference between BLs and ground, while disabling all YSWBj and YSWRB0 where j=0, 1, . . . , m−1.

The programmable resistive devices can be used to construct a memory in accordance with one embodiment. FIG. 16( a) shows a portion of a programmable resistive memory 100 constructed by an array 101 of 3-terminal MRAM cells 110 in n rows and m+1 columns and n pairs of wordline drivers 150-i and 151-i, where i=0,1, . . . , n−1, according to one embodiment. The memory array 101 has m normal columns and one reference column for one shared sense amplifier 140 for differential sensing. Each of the memory cells 110 has a resistive element 111 coupled to the P terminal of a program-0 diode 112 and N terminal of a program-1 diode 113. The program-0 diode 112 and the program-1 diode 113 serve as program selectors. Each resistive element 111 is also coupled to a bitline BLj 170-j (j=0,1, . . . m−1) or reference bitline BLR0 175-0 for those of the memory cells 110 in the same column. The N terminal of the diode 112 is coupled to a wordline WLNi 152-i through a local wordline LWLNi 154-i, where i=0,1, . . . , n−1, for those of the memory cells 110 in the same row. The P terminal of the diode 113 is coupled to a wordline WLPi 153-i through a local wordline LWLPi 155-i, where i=0,1, . . . , n−1, for those cells in the same row. Each wordline WLNi or WLPi is coupled to at least one local wordline LWLNi or LWLPi, respectively, where i=0,1, . . . , n−1. The LWLNi 154-i and LWLPi 155-i are generally constructed by a high resistivity material, such as N well or polysilicon, to connect cells, and then coupled to the WLNi or WLPi (e.g., low-resistivity metal WLNi or WLPi) through conductive contacts or vias, buffers, or post-decoders 172-i or 173-i respectively, where i=0,1, . . . , n−1. Buffers or post-decoders 172-i or 173-i may be needed when using diodes as program selectors because there are currents flowing through WLNi or WLPi, especially when one WLNi or WLPi drivers multiple cells for program or read simultaneously in some embodiments. The wordlines WLNi and WLPi are driven by wordline drivers 150-i and 151-i, respectively, with a supply voltage vddi that can be switched between different voltages for program and read. Each BLj 170-j or BLR0 175-0 is coupled to a supply voltage VDDP through a Y-write-0 pass gate 120-j or 125 to program 0, where each BLj 170-j or BLR0 175-0 is selected by YS0WBj (j=0, 1, . . . , m−1) or YS0WRB0, respectively. Y-write-0 pass gate 120-j or 125 can be built by PMOS, though NMOS, diode, or bipolar devices can be employed in other embodiments. Similarly, each BLj 170-j or BLR0 175-0 is coupled to a supply voltage 0V through a Y-write-1 pass gate 121-j or 126 to program 1, where each BLj 1701 or BLR0 175-0 is selected by YS1Wj (j=0, 1, . . . , m−1) or YS1WR0, respectively. Y-write-1 pass gate 121-j or 126 is can be built by NMOS, though PMOS, diode, or bipolar devices can be employed in other embodiments. Each BL or BLR0 is coupled to a dataline DL or DLR0 through a Y-read pass gate 130-j or 135 selected by YSRj (j=0,1, . . . , m−1) or YSRR0, respectively. In this portion of memory array 101, m normal datalines DLj (j=0,1, . . . , m−1) are connected to an input 160 of a sense amplifier 140. Reference dataline DLR0 provides another input 161 for the sense amplifier 140, except that no multiplex is generally needed in a reference branch. The output of the sense amplifier 140 is Q0.

To program a 0 into a cell, the specific WLNi, WLPi and BLj are selected as shown in FIG. 13( a) or 13(b) by wordline drivers 150-i, 151-i, and Y-pass gate 120-j by YS0WBj, respectively, where i=0,1, . . . n−1 and j=0,1, . . . , m−1, while the other wordlines and bitlines are also properly set. A high voltage is applied to VDDP. In some embodiments, the reference cells can be programmed into 0 by setting proper voltages to WLRNi 158-i, WLRPi 159-i and YS0WRB0, where i=0,1, . . . , n−1. To program a 1 to a cell, the specific WLNi, WLPi and BLj are selected as shown in FIG. 12( a) or 12(b) by wordline driver 150-i, 151-i, and Y-pass gate 121-j by YS1 Wj, respectively, where i=0,1, . . . n−1 and j=0,1, . . . , m−1, while the other wordlines and bitlines are also properly set. In some embodiments, the reference cells can be programmed to 1 by setting proper voltages to WLRNi 158-i, WLRPi 159-i and YS1WR0, where i=0,1, . . . , n−1. To read a cell, a data column 160 can be selected by turning on the specific WLNi, WLPi and YSRj, where i=0,1, . . . , n−1, and j=0,1, . . . , m−1, and a reference cell coupled to the reference dataline DLR 161 for the sense amplifier 140 to sense and compare the resistance difference between BLs and ground, while disabling all YS0WBj, YS0WRB0, YS1Wj and YS1WR0, where j=0, 1, . . . , m−1.

Another embodiment of constructing an MRAM memory with 2-terminal MRAM cells is shown in FIG. 16( b), provided the voltage difference VDDP, between high and low states, is less than twice of the diode's threshold voltage Vd, i.e., VDDP<2*Vd. As shown in FIG. 16( b), two wordlines per row WLNi 152-i and WLPi 153-i in FIG. 16( a) can be merged into one wordline driver WLNi 152-i, where i=0,1, . . . , n−1. Also, the local wordlines LWLNi 154-i and LWLP 155-i per row in FIG. 16( a) can be merged into one local wordline LWLNi 154-i, where i=0,1, . . . , n−1, as shown in FIG. 16( b). Still further, two wordline drivers 150-i and 151-i in FIG. 16( a) can be merged into one, i.e., wordline driver 150-i. The BLs and WLNs of the unselected cells are applied with proper program 1 and 0 conditions as shown in FIGS. 14( a) and 14(b), respectively. Since half of wordlines, local wordlines, and wordline drivers can be eliminated in this embodiment, cell and macro areas can be reduced substantially.

Differential sensing is a common for programmable resistive memory, though single-end sensing can be used in other embodiments. FIGS. 17( a), 17(b), and 17(c) show three other embodiments of constructing reference cells for differential sensing. In FIG. 17( a), a portion of memory 400 has a normal array 180 of n×m cells, two reference columns 150-0 and 150-1 of n×1 cells each storing all data 0 and 1 respectively, m+1 Y-read pass gates 130, and a sense amplifier 140. As an example, n=8 and m=8 are used to illustrate the concept. There are n wordlines WLBi and n reference wordlines WLRBi for each column, where i=0,1, . . . , n−1. When a wordline WLBi is turned on to access a row, a corresponding reference wordline WLRBi (i=0,1, . . . , n−1) is also turned on to activate two reference cells 170-0 and 170-1 in the same row to provide mid-level resistance after proper scaling in the sense amplifier. The selected dataline 160 along with the reference dataline 161 are input to a sense amplifier 140 to generate an output Q0. In this embodiment, each WLRBi and WLBi (i=0,1, . . . , n−1) are hardwired together and every cells in the reference columns need to be pre-programmed before read.

FIG. 17( b) shows another embodiment of using a reference cell external to a reference column. In FIG. 17( b), a portion of memory 400 has a normal array 180 of n×m cells, a reference column 150 of n×1 cells, m+1 Y-read pass gates 130, and a sense amplifier 140. When a wordline WLBi (i=0,1, . . . , n−1) is turned on, none of the cells in the reference column 150 are turned on. An external reference cell 170 with a pre-determined resistance is turned on instead by an external reference wordline WLRB. The selected dataline 160 and the reference dataline 161 are input to a sense amplifier 140 to generate an output Q0. In this embodiment, all internal reference wordlines WLRBi (i=0,1, . . . , n−1) in each row are tied together to a high voltage to disable the diodes in the reference column. The reference column 150 provides a loading to match with that of the normal columns.

FIG. 17( c) shows another embodiment of constructing reference cells for differential sensing. In FIG. 17( c), a portion of memory 400 has a normal array 180 of n×m cells, one reference column 150 of n×1, two reference rows 175-0 and 175-1 of 1×m cells, m+1 Y-read pass gates 130, and a sense amplifier 140. As an example, n=8 and m=8 are used to illustrate the approach. There are n wordlines WLBi and 2 reference wordlines WLRB0 175-0 and WLRB1 175-1 on top and bottom of the array, where i=0,1, . . . , n−1. When a wordline WLBi (i=0,1, . . . , n−1) is turned on to access a row, the reference wordline WLRB0 and WLRB1 are also turned on to activate two reference cells 170-0 and 170-1 in the upper and lower right corners of the array 180, which store data 0 and 1 respectively. The selected dataline 160 along with the reference dataline 161 are input to a sense amplifier 140 to generate an output Q0. In this embodiment, all cells in the reference column 150 are disabled except that the cells 170-0 and 170-1 on top and bottom of the reference column 150. Only two reference cells are used for the entire n×m array that needs to be pre-programmed before read.

For those programmable resistive devices that have a very small resistance ratio between states 1 and 0, such as 2:1 ratio in MRAM, FIGS. 17( a) and 17(c) are desirable embodiments, depending on how many cells are suitable for one pair of reference cells. Otherwise, FIG. 17( b) is a desirable embodiment for electrical fuse or PCM that has resistance ratio of more than about 10.

FIGS. 15, 16(a), 16(b), 17(a), 17(b), and 17(c) show only a few embodiments of a portion of programmable resistive memory in a simplified manner. The memory array 101 in FIGS. 15, 16(a), and 16(b) can be replicated s times to read or program s-cells at the same time. In the case of differential sensing, the number of reference columns to normal columns may vary and the physical location can also vary relative to the normal data columns. Rows and columns are interchangeable. The numbers of rows, columns, or cells likewise may vary. For those skilled in the art understand that the above descriptions are for illustrative purpose. Various embodiments of array structures, configurations, and circuits are possible and are still within the scope of this invention.

The portions of programmable resistive memories shown in FIGS. 15, 16(a), 16(b), 17(a), 17(b) and 17(c) can include different types of resistive elements. The resistive element can be an electrical fuse including a fuse fabricated from an interconnect, contact/via fuse, contact/via anti-fuse, or gate oxide breakdown anti-fuse. The interconnect fuse can be formed from silicide, metal, metal alloy, or some combination thereof, or can be constructed from a CMOS gate. The resistive element can also be fabricated from phase-change material, MTJ, etc. For the electrical fuse fabricated from an interconnect, contact, or via fuse, programming requirement is to provide a sufficiently high current, about 4-20 mA range, for a few microseconds to blow the fuse by electro-migration, heat, ion diffusion, or some combination thereof. For anti-fuse, programming requirement is to provide a sufficiently high voltage to breakdown the dielectrics between two ends of a contact, via or CMOS gate. The required voltage is about 6-7V for a few millisecond to consume about 10 uA of current in today's technologies. Programming Phase-Change Memory (PCM) requires different voltages and durations for 0 and 1. Programming to a 1 (or to reset) requires a high and short voltage pulse applied to the phase-change film. Alternatively, programming to a 0 (or to set) requires a low and long voltage pulse applied to the phase change film. The reset needs about 3V for 50 ns and consumes about 300 uA, while set needs about 2V for 300 ns and consumes about 100 uA. For MRAM, the high and low program voltages are about 2-3V and 0V, respectively, and the current is about +/−100-200 uA.

Most programmable resistive devices have a higher voltage VDDP (˜2-3V) for programming than the core logic supply voltage VDD (˜1.0V) for reading. FIG. 18( a) shows a schematic of a wordline driver circuit 60 according to one embodiment. The wordline driver includes devices 62 and 61, as shown as the wordline driver 150 in FIGS. 15, 16(a) and 16(b). The supply voltage vddi is further coupled to either VDDP or VDD through power selectors 63 and 64 (e.g., PMOS power selectors) respectively. The input of the wordline driver Vin is from an output of an X-decoder. In some embodiments, the power selectors 63 and 64 are implemented as thick oxide I/O devices to sustain high voltage. The bodies of power selector 63 and 64 can be tied to vddi to prevent latchup.

Similarly, bitlines tend to have a higher voltage VDDP (˜2-3V) for programming than the core logic supply voltage VDD (˜1.0V) for reading. FIG. 18( b) shows a schematic of a bitline circuit 70 according to one embodiment. The bitline circuit 70 includes a bitline (BL) coupled to VDDP and VDD through power selectors 73 and 74 (e.g., PMOS power selectors), respectively. If the bitline needs to sink a current such as in an MRAM, an NMOS pulldown device 71 can be provided. In some embodiments, the power selectors 73 and 74 as well as the pulldown device 71 can be implemented as thick-oxide I/O devices to sustain high voltage. The bodies of power selector 73 and 74 can be tied to vddi to prevent latchup.

Using diodes as program selectors may have high leakage current if a memory size is very large. Power selectors for a memory can help reducing leakage current by switching to a lower supply voltage or even turning off when a portion of memory is not in use. FIG. 18( c) shows a portion of memory 85 with an internal power supply VDDP coupled to an external supply VDDPP and a core logic supply VDD through power selectors 83 and 84. VDDP can even be coupled to ground by an NMOS pulldown device 81 to disable this portion of memory 85, if this portion of memory is temporarily not in use.

FIG. 19( a) shows one embodiment of a schematic of a pre-amplifier 100 according to one embodiment. The pre-amplifier 100 needs special considerations because the supply voltage VDD for core logic devices is about 1.0V that does not have enough head room to turn on a diode to make sense amplifiers functional, considering a diode's threshold is about 0.7V. One embodiment is to use another supply VDDR, higher than VDD, to power at least the first stage of sense amplifiers. The programmable resistive cell 110 shown in FIG. 19( a) has a resistive element 111 and a diode 112 as program selector, and can be selected for read by asserting YSR′ to turn on a gate of a MOS 130 and wordline bar WLB. The MOS 130 is Y-selected pass gate to select a signal from one of the at least one bitline(s) (BL) coupled to cells to a dataline (DL) for sensing. The pre-amplifier 100 also has a reference cell 115 including a reference resistive element 116 and a reference diode 117. The reference cell 115 can be selected for differential sensing by asserting YSRR′ to turn on a gate of a MOS 131 and reference wordline WLRB. The MOS 131 is a reference pass gate to pass a signal from a reference bitline (BLR) to a reference dataline (DLR) for sensing. YSRR′ is similar to YSR′ to turn on a reference cell rather than a selected cell, except that the reference branch typically has only one reference bitline (BLR). The resistance Ref of the reference resistive element 116 can be set at a resistance half-way between minimum of state 1 and maximum of state 0 resistance. MOS 151 is for pre-charging DL and DLR to the same voltage before sensing by a pre-charge signal Vpc. Alternatively, the DL and DLR can be pre-charged to ground or to a diode voltage above ground in other embodiments.

The drains of MOS 130 and 131 are coupled to sources of MOS 132 and 134, respectively. The gates of 132 and 134 are biased at a fixed voltage Vbias. The channel width to length ratios of NMOS 132 and 134 can be relatively large to clamp the voltage swings of dataline DL and reference dataline DLR, respectively. The drain of NMOS 132 and 134 are coupled to drains of PMOS 170 and 171, respectively. The drain of PMOS 170 is coupled to the gate of PMOS 171 and the drain of PMOS 171 is coupled to the gate of PMOS 170. The outputs V+ and V− of the pre-amplifier 100 are the drains of PMOS 170 and PMOS 171 respectively. The sources of PMOS 170 and PMOS 171 are coupled to a read supply voltage VDDR. The outputs V+ and V− are pulled up by a pair of PMOS 175 to VDDR when the pre-amplifier 100 is disabled. VDDR is about 2-3V (which is higher than about 1.0V VDD of core logic devices) to turn on the diode selectors 112 and 117 in the programmable resistive cell 110 and the reference cell 115, respectively. The CMOS 130, 131, 132, 134, 170, 171, and 175 can be embodied as thick-oxide I/O devices to sustain high voltage VDDR. The NMOS 132 and 134 can be native NMOS (i.e. the threshold voltage is ˜0V) to allow operating at a lower VDDR. In another embodiment, the read selectors 130 and 131 can be PMOS devices. In another embodiment, the sources of PMOS 170 and 171 can be coupled to the drain of a PMOS pullup (an activation device not shown in FIG. 19( a)), whose source is then coupled to VDDR. This sense amplifier can be activated by setting the gate of the PMOS pullup low after turning on the reference and Y-select pass gates.

FIG. 19( b) shows one embodiment of a schematic of an amplifier 200 according to one embodiment. In another embodiment, the outputs V+ and V− of the pre-amplifier 100 in FIG. 19( a) can be coupled to gates of NMOS 234 and 232, respectively, of the amplifier 200. The NMOS 234 and 232 can be relatively thick oxide I/O devices to sustain the high input voltage V+ and V− from a pre-amplifier. The sources of NMOS 234 and 232 are coupled to drains of NMOS 231 and 230, respectively. The sources of NMOS 231 and 230 are coupled to a drain of an NMOS 211. The gate of NMOS 211 is coupled to a clock φ to turn on the amplifier 200, while the source of NMOS 211 is coupled to ground. The drains of NMOS 234 and 232 are coupled to drains of PMOS 271 and 270, respectively. The sources of PMOS 271 and 270 are coupled to a core logic supply VDD. The gates of PMOS 271 and NMOS 231 are connected and coupled to the drain of PMOS 270, as a node Vp. Similarly, the gates of PMOS 270 and NMOS 230 are connected and coupled to the drain of PMOS 271, as a node Vn. The nodes Vp and Vn are pulled up by a pair of PMOS 275 to VDD when the amplifier 200 is disabled when φ goes low. The output nodes Vout+ and Vout− are coupled to nodes Vn and Vp through a pair of inverters as buffers.

FIG. 19( c) shows a timing diagram of the pre-amplifier 100 and the amplifier 200 in FIGS. 19( a) and 19(b), respectively. The X- and Y-addresses AX/AY are selected to read a cell. After some propagation delays, a cell is selected for read by turning WLB low and YSR high to thereby select a row and a column, respectively. Before activating the pre-amplifier 100, a pulse Vpc can be generated to precharge DL and DLR to ground, to a diode voltage above ground, or to each other. The pre-amplifier 100 would be very slow if the DL and DLR voltages are high enough to turn off the cascode devices (e.g., NMOS 132 and 134). After the pre-amplifier outputs V+ and V− are stabilized, the clock φ is set high to turn on the amplifier 200 and to amplify the final output Vout+ and Vout− into full logic levels.

FIG. 20( a) shows another embodiment of a pre-amplifier 100′, similar to the pre-amplifier 100 in FIG. 19( a), with PMOS pull-ups 171 and 170 configured as current-mirror loads. The reference branch can be turned on by a level signal, SAEN, to enable the sense amplifier, a cycle-by-cycle signal YSRR′ as in FIG. 19( a). MOS 151 is for pre-charging DL and DLR to the same voltage before sensing by a pre-charge signal Vpc. Alternatively, the DL or DLR can be pre-charged to ground or to a diode voltage above ground in other embodiments. In this embodiment, the number of the reference branches can be shared at the expense of increasing power consumption.

FIG. 20( b) shows level shifters 300 according to one embodiment. The V+ and V− from the pre-amplifier 100, 100′ outputs in FIG. 19( a) or FIG. 20( a) are coupled to gates of NMOS 301 and 302, respectively. The drains of NMOS 301 and 302 are coupled to a supply voltage VDDR. The sources of NMOS 301 and 302 are coupled to drains of NMOS 303 and 304, respectively, which have gates and drains connected as diodes to shift the voltage level down by one Vtn, the threshold voltage of an NMOS. The sources of NMOS 303 and 304 are coupled to the drains of pulldown devices NMOS 305 and 306, respectively. The gates of NMOS 305 and 306 can be turned on by a clock φ. The NMOS 301, 302, 303 and 304 can be thick-oxide I/O devices to sustain high voltage VDDR. The NMOS 303 and 304 can be cascaded more than once to shift V+ and V− further to proper voltage levels Vp and Vn. In another embodiment, the level shifting devices 303 and 304 can be built using PMOS devices.

FIG. 20( c) shows another embodiment of an amplifier 200′ with current-mirror loads having PMOS 270 and 271. The inputs Vp and Vn of the amplifier 200′ are from the outputs Vp and Vn of the level shifter 300 in FIG. 20( b) can be coupled to gates of NMOS 231 and 230, respectively. The drains of NMOS 231 and 230 are coupled to drains of PMOS 271 and 270 which provide current-mirror loads. The drain and gate of PMOS 271 are connected and coupled to the gate of PMOS 270. The sources of NMOS 231 and 230 are coupled to the drain of an NMOS 211, which has the gate coupled to a clock signal φ and the source to ground. The clock signal φ enables the amplifier 200. The drain of PMOS 270 provides an output Vout+. The PMOS pullup 275 keeps the output Vout+ at logic high level when the amplifier 200′ is disabled.

FIG. 20( d) shows one embodiment of a pre-amplifier 100′ based on all core devices according to one embodiment. The programmable resistive cell 110′ has a resistive element 111′ and a diode 112′ as program selector that can be selected for read by asserting YSR′ to turn on a gate of a MOS 130′ and wordline bar WLB. The MOS 130′ is Y-select pass gate to select a signal from one of the at least one bitline(s) (BL) coupled to cells to a dataline (DL) for sensing. The pre-amplifier 100′ also has a reference cell 115′ including a reference resistive element 116′ and a reference diode 117′. The reference cell 115′ can be selected for differential sensing by asserting YSRR′ to turn on a gate of a MOS 131′ and reference wordline WLRB. The MOS 131′ is a reference pass gate to pass a signal from a reference bitline (BLR) to a reference dataline (DLR) for sensing. YSRR′ is similar to YSR′ to turn on a reference cell rather than a selected cell, except that the reference branch typically has only one reference bitline (BLR). The drains of MOS 130′ and 131′ are coupled to drains of PMOS 170′ and 171′, respectively. The gate of 170′ is coupled to the drain of 171′ and the gate of 171′ is coupled to the drain of 170′. The sources of MOS 170′ and 171′ are coupled to drains of MOS 276′ and 275′, respectively. The gate of 275′ is coupled to the drain of 276′ and the gate of 276′ is coupled to the drain of 275′. The drains of 170′ and 171′ are coupled by a MOS equalizer 151′ with a gate controlled by an equalizer signal Veq1. The drains of 276′ and 275′ are coupled by a MOS equalizer 251′ with a gate controlled by an equalizer signal Veq0. The equalizer signals Veq0 and Veq1 are preferably dc signals to reduce the voltage swing in the drains of 170′, 171′ and 275′, 276′, respectively. By reducing the voltage swings of the PMOS devices in the pullup and by stacking more than one level of cross-coupled PMOS, the voltage swings of the 170′, 171′, 275′, and 276′ can be reduced to VDD range so that core logic devices can be used. For example, the supply voltage of the sense amplifier VDDR is about 2.5V, while the VDD for core logic devices is about 1.0V. The DL and DLR are about 1 V, based on diode voltage of about 0.7V with a few hundred millivolts (mV) drop for resistors and pass gates. If the cross-coupled PMOS are in two-level stacks, each PMOS only endures voltage stress of (2.5-1.0)/2=0.75V. Alternatively, merging MOS 275′ and 276′ into a single MOS or using a junction diode in the pullup is another embodiment. Inserting low-Vt NMOS as cascode devices between 170′ and 130′; 171′ and 131′ is another embodiment. The output nodes from the drains of 170′ and 171′ are about 1.0-1.2V so that the sense amplifier as shown in FIG. 19( b) can be used with all core logic devices.

FIG. 20( e) shows another embodiment of a pre-amplifier 100″ with an activation device 275″ according to one embodiment. The programmable resistive cell 110″ has a resistive element 111″ and a diode 112″ as program selector that can be selected for read by asserting YSR″ to turn on a gate of a MOS 130″ and wordline bar WLB. The MOS 130″ is Y-select pass gate to select a signal from one of the at least one bitline(s) (BL) coupled to cells to a dataline (DL) for sensing. The pre-amplifier 100″ also has a reference cell 115″ including a reference resistive element 116″ and a reference diode 117″. The reference cell 115″ can be selected for differential sensing by asserting YSRR″ to turn on a gate of a MOS 131″ and reference wordline WLRB. The MOS 131″ is a reference pass gate to pass a signal from a reference bitline (BLR) to a reference dataline (DLR) for sensing. YSRR″ is similar to YSR″ to turn on a reference cell rather than a selected cell, except that the reference branch typically has only one reference bitline (BLR). The drains of MOS 130″ and 131″ are coupled to the sources of MOS 132″ and 134″, respectively. The drains of MOS 132″ and 134″ are coupled to the drains of PMOS 170″ and 171″, respectively. The gate of 170″ is coupled to the drain of 171″ and the gate of 171″ is coupled to the drain of 170″. The sources of MOS 170″ and 171″ are coupled to the drain of MOS 275″ whose source is coupled to a supply voltage and gate coupled to a Sensing Enable Bar (SEB). The drains of 170″ and 171″ are coupled by a MOS equalizer 251″ with a gate controlled by an equalizer signal Veq0. The sources of 132″ and 134″ are coupled by a MOS equalizer 151″ with a gate controlled by an equalizer signal Veq1. The equalizer signals Veq0 and Veq1 can be dc or ac signals to reduce the voltage swings in the sources of 170″, 171″ and 132″, 134″, respectively.

FIGS. 19( a), 20(a), 20(d) and 20(d) only show four of many pre-amplifier embodiments. Similarly, FIGS. 19( b), 20(b) and 20(c) only show several of many amplifier and level shifter embodiments. Various combinations of pre-amplifiers, level shifters, and amplifiers in NMOS or PMOS, in core logic or I/O devices, with devices stacked or with an activation device, or operated under high voltage VDDR or core device supply VDD can be constructed differently, separately, or mixed. The equalizer devices can be embodied as PMOS or NMOS, and can be activated by a dc or ac signal.

FIGS. 21( a) and 21(b) show a flow chart depicting embodiments of a program method 700 and a read method 800, respectively, for a programmable resistive memory in accordance with certain embodiments. The methods 700 and 800 are described in the context of a programmable resistive memory, such as the programmable resistive memory 100 in FIGS. 15, 16(a) and 16(c). In addition, although described as a flow of steps, one of ordinary skilled in the art will recognize that at least some of the steps may be performed in a different order, including simultaneously, or skipped.

FIG. 21( a) depicts a method 700 of programming a programmable resistive memory in a flow chart according to one embodiment. In the first step 710, proper power selectors can be selected so that high voltages can be applied to the power supplies of wordline drivers and bitlines. In the second step 720, the data to be programmed in a control logic (not shown in FIGS. 15, 16(a), and 16(b)) can be analyzed, depending on what types of programmable resistive devices. For electrical fuse, this is a One-Time-Programmable (OTP) device such that programming always means blowing fuses into a non-virgin state and is irreversible. Program voltage and duration tend to be determined by external control signals, rather than generated internally from the memory. For PCM, programming into a 1 (to reset) and programming into a 0 (to set) require different voltages and durations such that a control logic determines the input data and select proper power selectors and assert control signals with proper timings. For MRAM, the directions of current flowing through MTJs are more important than time duration. A control logic determines proper power selectors for wordlines and bitlines and assert control signals to ensure a current flowing in the desired direction for desired time. In the third step 730, a cell in a row can be selected and the corresponding local wordline can be turned on. In the fourth step 740, sense amplifiers can be disabled to save power and prevent interference with the program operations. In the fifth step 750, a cell in a column can be selected and the corresponding Y-write pass gate can be turned on to couple the selected bitline to a supply voltage. In the last step 760, a desired current can be driven for a desired time in an established conduction path to complete the program operations. For most programmable resistive memories, this conduction path is from a high voltage supply through a bitline select, resistive element, diode as program selector, and an NMOS pulldown of a local wordline driver to ground. Particularly, for programming a 1 to an MRAM, the conduction path is from a high voltage supply through a PMOS pullup of a local wordline driver, diode as program selector, resistive element, and bitline select to ground.

FIG. 21( b) depicts a method 800 of reading a programmable resistive memory in a flow chart according to one embodiment. In the first step 810, proper power selectors can be selected to provide supply voltages for local wordline drivers, sense amplifiers, and other circuits. In the second step 820, all Y-write pass gates, i.e. bitline program selectors, can be disabled. In the third step 830, desired local wordline(s) can be selected so that the diode(s) as program selector(s) have a conduction path to ground. In the fourth step 840, sense amplifiers can be enabled and prepared for sensing incoming signals. In the fifth step 850, the dataline and the reference dataline can be pre-charged to the V− voltage of the programmable resistive device cell. In the sixth step 860, the desired Y-read pass gate can be selected so that the desired bitline is coupled to an input of the sense amplifier. A conduction path is thus established from the bitline to the resistive element in the desired cell, diode(s) as program selector(s), and the pulldown of the local wordline driver(s) to ground. The same applies for the reference branch. In the last step 870, the sense amplifiers can compare the read current with the reference current to determine a logic output of 0 or 1 to complete the read operations.

FIG. 22 shows a processor system 700 according to one embodiment. The processor system 700 can include a programmable resistive device 744, such as in a cell array 742, in memory 740, according to one embodiment. The processor system 700 can, for example, pertain to a computer system. The computer system can include a Central Process Unit (CPU) 710, which communicate through a common bus 715 to various memory and peripheral devices such as I/O 720, hard disk drive 730, CDROM 750, memory 740, and other memory 760. Other memory 760 is a conventional memory such as SRAM, DRAM, or flash, typically interfaces to CPU 710 through a memory controller. CPU 710 generally is a microprocessor, a digital signal processor, or other programmable digital logic devices. Memory 740 is preferably constructed as an integrated circuit, which includes the memory array 742 having at least one programmable resistive device 744. The memory 740 typically interfaces to CPU 710 through a memory controller. If desired, the memory 740 may be combined with the processor, for example CPU 710, in a single integrated circuit.

The invention can be implemented in a part or all of an integrated circuit in a Printed Circuit Board (PCB), or in a system. The programmable resistive device can be fuse, anti-fuse, or emerging nonvolatile memory. The fuse can be silicided or non-silicided polysilicon fuse, thermally isolated active region fuse, local interconnect fuse, metal fuse, contact fuse, or via fuse. The anti-fuse can be a gate-oxide breakdown anti-fuse, contact or via anti-fuse with dielectrics in-between. The emerging nonvolatile memory can be Magnetic RAM (MRAM), Phase Change Memory (PCM), Conductive Bridge RAM (CBRAM), or Resistive RAM (RRAM). Though the program mechanisms are different, their logic states can be distinguished by different resistance values.

Same or additional information is provided in: (i) U.S. patent application Ser. No. 13/026,725, filed on Feb. 14, 2011, and entitled “CIRCUIT AND SYSTEM OF USING A JUNCTION DIODE AS PROGRAM SELECTOR FOR RESISTIVE DEVICES,” which is hereby incorporated herein by reference; and (ii) U.S. patent application Ser. No. 13/026,650, filed on Feb. 14, 2011, and entitled “CIRCUIT AND SYSTEM OF USING POLYSILICON DIODE AS PROGRAM SELECTOR FOR RESISTIVE DEVICES IN CMOS LOGIC PROCESSES,” which is hereby incorporated herein by reference.

The above description and drawings are only to be considered illustrative of exemplary embodiments, which achieve the features and advantages of the present invention. Modifications and substitutions of specific process conditions and structures can be made without departing from the spirit and scope of the present invention.

The many features and advantages of the present invention are apparent from the written description and, thus, it is intended by the appended claims to cover all such features and advantages of the invention. Further, since numerous modifications and changes will readily occur to those skilled in the art, it is not desired to limit the invention to the exact construction and operation as illustrated and described. Hence, all suitable modifications and equivalents may be resorted to as falling within the scope of the invention. 

What is claimed is:
 1. A sense amplifier in a programmable resistive memory comprises: a reference branch having at least a first MOS transistor of a first type, the first MOS transistor having a source terminal coupled to receive a first supply voltage, a gate terminal coupled to a drain terminal, and both the gate terminal and the drain terminal being coupled to a drain terminal of a second MOS transistor of a second type, the second MOS transistor having a gate terminal coupled to receive a bias supply voltage, and a source terminal coupled to a reference resistor and through the reference resistor further coupled to a diode which in turn is coupled to receive a second supply voltage; a sensing branch having at least a third MOS transistor of the first type, the third MOS transistor having a source terminal coupled to receive the first supply voltage, and a drain terminal coupled to a drain terminal of a fourth MOS transistor of the second type, the fourth MOS transistor having the gate terminal coupled to receive the bias supply voltage, and a source terminal coupled to a programmable resistance device cell and through the programmable resistance device cell further coupled to receive the second supply voltage, the programmable resistance device cell including a programmable resistance element coupled to a diode as a selector, wherein the gate terminal of the third MOS transistor is coupled to the gate terminal of the first MOS transistor; wherein the resistance difference between the reference resistor and the programmable resistance element is sensed through the drain terminal of the third MOS transistor in the sensing branch into a logic level, and wherein the magnitude of the voltage difference between the first and second supply voltages is larger than a supply voltage for core logic devices of the programmable resistive memory.
 2. A sense amplifier as recited in claim 1, wherein the diode in the sensing branch has at least one first type of active region having a first type of dopant and a second type of active region having a second type of dopant, and wherein both of the active regions reside in a common well isolated from the silicon substrate that houses one type of MOS transistor.
 3. A sense amplifier as recited in claim 1, wherein the diode in the sensing branch has at least one first type of region having a first type of dopant and a second type of region having a second type of dopant, wherein both of the regions reside in a polysilicon structure.
 4. A sense amplifier as recited in claim 1, wherein the programmable resistive memory include a memory array of cells, and wherein between the fourth MOS transistor and the programmable resistance cell in the sensing branch there is at least one MOS device to select a specific cell in one dimension of the memory array for sensing.
 5. A sense amplifier as recited in claim 1, wherein between the diode and the second supply voltage in the sensing branch there is at least one MOS device to select a specific cell in another dimension of the cell array for sensing.
 6. A sense amplifier as recited in claim 1, wherein the second type of MOS devices in the reference and sensing branches are native MOS.
 7. A sense amplifier as recited in claim 1, wherein at least one of the MOS devices in the sensing or reference branch are core logic devices.
 8. A sense amplifier as recited in claim 1, wherein at least one of the nodes between the corresponding sensing and reference brances are coupled by a MOS in the source and drain as an equalizer.
 9. A sense amplifier in a programmable resistive memory comprises: a reference branch having at least one stack of a first MOS transistor of a first type, with a source terminal of the first MOS transistor in one stack being coupled to a drain terminal of the first MOS transistor in another stack, and with a gate terminal being coupled to the drain terminal of the same first MOS transistor in the same stack, wherein the stack having a source terminal in one end coupled to a first supply voltage terminal, and the drain terminal in the other end coupled to a drain terminal of a second MOS transistor of a second type, the second MOS transistor having a gate terminal coupled to a bias supply voltage terminal, and a source terminal coupled to a reference resistor and through the reference resistor further couples to a diode which in turn couples to a second supply voltage terminal; a sensing branch having at least one stack of a third MOS transistor of a first type, with a source terminal of the third MOS transistor in one stack being coupled to a drain terminal of the third MOS transistor in another stack, wherein the stack having a source terminal in one end coupled to a first supply voltage terminal, and a drain terminal in the other end coupled to a drain terminal of a fourth MOS transistor of a second type, the fourth MOS transistor having a gate terminal coupled to a bias supply voltage terminal, and a source terminal coupled to a programmable resistance device cell and through the programmable resistance device cell further coupled to the second supply voltage terminal, the programmable resistance device cell including a programmable resistance element coupled to a diode, wherein the gate terminal of the third MOS transistor in the sensing branch is coupled to the gate terminal of the first MOS transistor in the reference branch in the same stack; wherein the resistance difference between the reference resistor and the programmable resistance element is sensed through the drain terminal of the third MOS transistor in the sensing branch into a logic level, and wherein the magnitude of the voltage difference between voltages at the first and second supply voltage terminals is larger than a supply voltage for core logic devices of the programmable resistive memory.
 10. A sense amplifier as recited in claim 4, wherein at least one of the MOS devices in the sensing or reference branch are core logic devices.
 11. A sense amplifier in a programmable resistive memory comprises: a reference branch having at least a first MOS transistor of a first type, the first MOS transistor having a source terminal coupled to receive a first supply voltage, a gate terminal coupled to a drain terminal, and both the gate terminal and the drain terminal being coupled to a drain terminal of a second MOS transistor of a second type, the second MOS transistor having a gate terminal coupled to receive a bias supply voltage, and a source terminal coupled to a reference resistor and through the reference resistor further coupled to a selector which in turn is coupled to receive a second supply voltage; a sensing branch having at least a third MOS transistor of the first type, the third MOS transistor having a source terminal coupled to receive the first supply voltage, and a drain terminal coupled to a drain terminal of a fourth MOS transistor of the second type, the fourth MOS transistor having the gate terminal coupled to receive the bias supply voltage, and a source terminal coupled to a programmable resistance device cell and through the programmable resistance device cell further coupled to receive the second supply voltage, the programmable resistance device cell including a programmable resistance element coupled to a selector, wherein the gate terminal of the third MOS transistor is coupled to the gate terminal of the first MOS transistor; wherein the resistance difference between the reference resistor and the programmable resistance element is sensed through the drain terminal of the third MOS transistor in the sensing branch into a logic level, and wherein the magnitude of the voltage difference between the first and second supply voltages is larger than a supply voltage for core logic devices of the programmable resistive memory.
 12. A sense amplifier as recited in claim 11, wherein the selector in the referencing or sensing branch has at least one first type of active region having a first type of dopant and a second type of active region having a second type of dopant, and wherein both of the active regions reside in a common well isolated from the silicon substrate that houses one type of MOS transistor.
 13. A sense amplifier as recited in claim 11, wherein the selector is a MOS.
 14. A sense amplifier as recited in claim 11, wherein the programmable resistive memory include a memory array of cells, and wherein between the fourth MOS transistor and the programmable resistance cell in the sensing branch there is at least one MOS device to select a specific cell in one dimension of the memory array for sensing.
 15. A sense amplifier as recited in claim 11, wherein between the program selector and the second supply voltage in the sensing branch there is at least one MOS device to select a specific cell in another dimension of the cell array for sensing.
 16. A sense amplifier as recited in claim 11, wherein the second type of MOS devices in the reference and sensing branches are native MOS.
 17. A sense amplifier as recited in claim 11, wherein at least one of the MOS devices in the sensing or reference branch are core logic devices.
 18. A sense amplifier as recited in claim 11, wherein at least one of the nodes between the corresponding sensing and reference branches are coupled by a MOS in the source and drain.
 19. A sense amplifier in a programmable resistive memory comprises: a reference branch having at least one stack of a first MOS transistor of a first type, with a source terminal of the first MOS transistor in one stack being coupled to a drain terminal of the first MOS transistor in another stack, and with a gate terminal being coupled to the drain terminal of the same first MOS transistor in the same stack, wherein the stack having a source terminal in one end coupled to a first supply voltage terminal, and the drain terminal in the other end coupled to a drain terminal of a second MOS transistor of a second type, the second MOS transistor having a gate terminal coupled to a bias supply voltage terminal, and a source terminal coupled to a reference resistor and through the reference resistor further couples to a selector which in turn couples to a second supply voltage terminal; a sensing branch having at least one stack of a third MOS transistor of a first type, with a source terminal of the third MOS transistor in one stack being coupled to a drain terminal of the third MOS transistor in another stack, wherein the stack having a source terminal in one end coupled to a first supply voltage terminal, and a drain terminal in the other end coupled to a drain terminal of a fourth MOS transistor of a second type, the fourth MOS transistor having a gate terminal coupled to a bias supply voltage terminal, and a source terminal coupled to a programmable resistance device cell and through the programmable resistance device cell further coupled to the second supply voltage terminal, the programmable resistance device cell including a programmable resistance element coupled to a selector, wherein the gate terminal of the third MOS transistor in the sensing branch is coupled to the gate terminal of the first MOS transistor in the reference branch in the same stack; wherein the resistance difference between the reference resistor and the programmable resistance element is sensed through the drain terminal of the third MOS transistor in the sensing branch into a logic level, and wherein the magnitude of the voltage difference between voltages at the first and second supply voltage terminals is larger than a supply voltage for core logic devices of the programmable resistive memory. 